IEEE MTT-V052-I03 (2004-03)

353 Pages·2004·17.106 MB·English

by  FANTOMASPING

IEEE TRANSACTIONS ON
MICROWAVE THEORY
AND TECHNIQUES
A PUBLICATION OF THE IEEE MICROWAVE THEORY AND TECHNIQUES SOCIETY
MARCH 2004 VOLUME 52 NUMBER 3 IETMAB (ISSN 0018-9480)
MINI-SPECIAL ISSUE ON THE 2003 IEEE MTT-S INTERNATIONAL MICROWAVE SYMPOSIUM
Editorial. .......... . ........ . ........ . . . ........ . ........ . ........ . . . ........ . ........ M. B. Steer 741
MINI-SPECIAL ISSUE PAPERS
60-GHz-Band Coplanar MMIC Active Filters . . . . . . . . . . . . . . . . . . M. Ito, K. Maruhashi, S. Kishimoto, and K. Ohara 743
A New 94-GHz Six-Port Collision-Avoidance Radar Sensor ........ E. Moldovan, S.-0. Tatu, T. Caman, K. Wu, and R. C. Bosisio 751
Nonorthogonality Relations Between Complex Hybrid Modes: An Application ror the Leaky-Wave Analysis or Laterally Shielded
Top-Open Planar Transmission Lines .. ..... ./. L. G. Tornero and A. A. Me!c6n 760
Coupling Matrix Extraction for Cascaded-Triplet (CT) Topology ..... . . .R. N. Gajaweera and L. F Lind 768
FDTD Modeling of Transient Microwave Signals in Dispersive and Lossy Bi-Isotropic Media
..... A. Grande, !. Barba, A. C. L. Cabeceira, ./. Represa, P. P. M. So, and W ./. R. Hoefer 773
Steady-Stale Analysis or Multilone Nonlinear Circuits in Wavelet Domain ..................... N. Soveiko and M. S. Nakhla 785
A Compact Enhanced-Bandwidth Hybrid Ring Using an Artiricial Lumped-Element Lert-Handed Transmission-Line Section ..... .
H. Okabe, C. Ca/oz, and T. Itoh 798
Hot Small-Signal 8-Paramctcr Measurements of Power Transistors Operating Under Large-Signal Conditions in a Load-Pull
Environment ror the Study or Nonlinear Parametric Interactions ............................................. .
. . . . . . . . . . . . . . . . . . . . . . . . . . . . T. Casseling, D. Barataud, S. Mons, 1.-M. Nebus, ./. P. Villotte, J. J. Obregon, and R. Quere 805
Evaluation or Signal-to-Noise and Distortion Ratio Degradation in Nonlinear Systems ............................... .
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . P. M. Lavrador, N. Borges de Carvalho, and./. C. Pedro 813
A Simpliried Analytic CAD Model for Linearly Tapered Microstrip Lines Including Losses ............................ .
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . C. L. Edwards, M. L. Edwards, S. Cheng, R. K. Stilwell, and C. C. Davis 823
Two Movable-Plate Nitride-Loaded MEMS Variable Capacitor . . . . . M. Bakri-Kassem and R.R. Mansour 831
/CJ
Range Correlation and J Performance Benefits in Single-Chip Silicon Doppler Radars for Noncontact Cardiopulmonary Monitoring
..... A. D. Droitcow; 0. Boric-Lubecke, V. M. Lubecke, J. Lin, and C. T. A. Kovacs 838
A Comprehensive Compact-Modeling Methodology ror Spiral Inductors in Silicon-Based RFTCs ........................ .
. . A. C. Watson, D. Melendy, P. Francis, K. Hwang, and A. Weiss/war 849
(Contents Continued on Back Cover)
+IEEE
MARCH2004 VOLUME52 NUMBER3 IETMAB (ISSN0018-9480)
MINI-SPECIALISSUEONTHE2003IEEEMTT-SINTERNATIONALMICROWAVESYMPOSIUM
Editorial.. ..... ...... ...... ...... ..... ...... ......... ...... ...... ..... ...... ...... ...... . M.B.Steer 741
MINI-SPECIALISSUEPAPERS
60-GHz-BandCoplanarMMICActiveFilters .... ...... ......... ...... ....M.Ito,K.Maruhashi,S.Kishimoto,andK.Ohata 743
ANew94-GHzSix-PortCollision-AvoidanceRadarSensor ......... ..E.Moldovan,S.-O.Tatu,T.Gaman,K.Wu,andR.G.Bosisio 751
Nonorthogonality Relations Between Complex Hybrid Modes: An Application for the Leaky-Wave Analysis of Laterally Shielded
Top-OpenPlanarTransmissionLines ... ..... ...... ....... ........ ...... ..... ....J.L.G.TorneroandA.Á.Melcón 760
CouplingMatrixExtractionforCascaded-Triplet(CT)Topology ... ...... ......... ..... ......R.N.GajaweeraandL.F.Lind 768
FDTDModelingofTransientMicrowaveSignalsinDispersiveandLossyBi-IsotropicMedia ...... ...... ...... ..... ....
...... ..... ...... ...... ...... ... A.Grande,I.Barba,A.C.L.Cabeceira,J.Represa,P.P.M.So,andW.J.R.Hoefer 773
Steady-StateAnalysisofMultitoneNonlinearCircuitsinWaveletDomain... ...... ........ ...... . N.SoveikoandM.S.Nakhla 785
ACompactEnhanced-BandwidthHybridRingUsinganArtificialLumped-ElementLeft-HandedTransmission-LineSection.. ....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... ..... ..... H.Okabe,C.Caloz,andT.Itoh 798
Hot Small-Signal S-Parameter Measurements of Power Transistors Operating Under Large-Signal Conditions in a Load–Pull
EnvironmentfortheStudyofNonlinearParametricInteractions.. ...... ...... ..... ...... ...... ...... ..... ....
...... ..... ...... ...... .....T.Gasseling,D.Barataud,S.Mons,J.-M.Nebus,J.P.Villotte,J.J.Obregon,andR.Quere 805
EvaluationofSignal-to-NoiseandDistortionRatioDegradationinNonlinearSystems ..... ...... ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...... ......P.M.Lavrador,N.BorgesdeCarvalho,andJ.C.Pedro 813
ASimplifiedAnalyticCADModelforLinearlyTaperedMicrostripLinesIncludingLosses.. ...... ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... C.L.Edwards,M.L.Edwards,S.Cheng,R.K.Stilwell,andC.C.Davis 823
TwoMovable-PlateNitride-LoadedMEMSVariableCapacitor .... ...... ......... ..... ..M.Bakri-KassemandR.R.Mansour 831
RangeCorrelationandI=QPerformanceBenefitsinSingle-ChipSiliconDopplerRadarsforNoncontactCardiopulmonaryMonitoring
...... ..... ...... ......... ...... ..... ...A.D.Droitcour,O.Boric-Lubecke,V.M.Lubecke,J.Lin,andG.T.A.Kovacs 838
AComprehensiveCompact-ModelingMethodologyforSpiralInductorsinSilicon-BasedRFICs.... ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ....A.C.Watson,D.Melendy,P.Francis,K.Hwang,andA.Weisshaar 849
(ContentsContinuedonBackCover)
(ContentsContinuedfromFrontCover)
CONTRIBUTEDPAPERS
Impact-IonizationEffectsontheHigh-FrequencyBehaviorofHFETs. ..... ....... ....... ...... . M.IslerandK.Schünemann 858
p-Type Multiplicative Schwarz (pMUS) Method With Vector Finite Elements for Modeling Three-Dimensional Waveguide
Discontinuities ...... ...... ...... ..... ...... ......... ...... ...... ..... ...... .....J.-F.LeeandD.-K.Sun 864
OptimizationofInP–InGaAsHPTGain:DesignofanOpto-MicrowaveMonolithicAmplifier ...... ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ......J.-L.Polleux,L.Paszkiewicz,A.-L.Billabert,J.Salset,andC.Rumelhard 871
ImplementationofanExactModalAbsorbingBoundaryTerminationConditionfortheApplicationoftheFinite-ElementTime-Domain
TechniquetoDiscontinuityProblemsinClosedHomogeneousWaveguides ...... ...... ........ ......T.-H.LohandC.Mias 882
AHybridMethodfortheEfficientCalculationoftheBandStructureof3-DMetallicCrystals ...... ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... ..... .M.G.SilveirinhaandC.A.Fernandes 889
PermittivityandPermeabilityMeasurementofMicrowavePackagingMaterials ....... .....G.Roussy,H.Chaabane,andH.Esteban 903
Broad-BandHBTBPSKandIQModulatorMMICsandMillimeter-WaveVectorSignalCharacterization .... ...... ..... ....
...... ..... ...... ...... ...... ..... ...H.-Y.Chang,T.-W.Huang,H.Wang,Y.-C.Wang,P.-C.Chao,andC.-H.Chen 908
AnAdaptiveAlgorithmforFastFrequencyResponseComputationofPlanarMicrowaveStructures .. ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... ..... . V.V.S.Prakash,J.Yeo,andR.Mittra 920
AmplifierLinearizationUsingCompactMicrostripResonantCell—TheoryandExperiment . .......T.Y.Yum,Q.Xue,andC.H.Chan 927
RigorousNetworkRepresentationofMicrowaveComponentsbytheUseofIndirectModeMatching . ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... .... I.D.StamatopoulosandI.D.Robertson 935
AnExperimentalStudyofScalabilityinShield-BasedOn-WaferCMOSTestFixtures....... ........ T.KaijaandE.O.Ristolainen 945
GeneralizedPoisson–NeumannPolygonalBasisFunctionsfortheElectromagneticSimulationofComplexPlanarStructures.. ....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... .... L.Knockaert,J.Sercu,andD.DeZutter 954
EnhancementoftheNumericalStabilityoftheAdaptiveIntegralMethodatLowFrequenciesThroughaLoop-ChargeFormulationof
theMethod-of-MomentsApproximation. ..... ....... ........ ...... .V.I.Okhmatovski,J.D.Morsey,andA.C.Cangellaris 962
DesignandFabricationofScanningNear-FieldMicrowaveProbesCompatibleWithAtomicForceMicroscopytoImageEmbedded
Nanostructures ...... ...... ...... ..... ....... ........ ...... ...... ..... ...... .. M.Tabib-AzarandY.Wang 971
ANovelCompositeRight-/Left-HandedCoupled-LineDirectionalCouplerWithArbitraryCouplingLevelandBroadBandwidth....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... ..... .....C.Caloz,A.Sanada,andT.Itoh 980
Eight-Channel 77-GHz Front-End Module With High-Performance Synthesized Signal Generator for FM-CW Sensor Applications
...... ..... ...... ...... ......... ..... ...... ...... ..W.Mayer,M.Meilchen,W.Grabherr,P.Nüchter,andR.Gühl 993
FullyMicromachinedFinite-GroundCoplanarLine-to-WaveguideTransitionsforW-BandApplications. .... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...... ...... .... Y.Lee,J.P.Becker,J.R.East,andL.P.B.Katehi 1001
ControlofBandstopResponseofHi–LoMicrostripLow-PassFilterUsingSlotinGroundPlane .... ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ......A.B.Abdel-Rahman,A.K.Verma,A.Boutejdar,andA.S.Omar 1008
RecyclingAmbientMicrowaveEnergyWithBroad-BandRectennaArrays .. ...... ..... ...... ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ....J.A.Hagerty,F.B.Helmbrecht,W.H.McCalpin,R.Zane,andZ.B.Popovic´ 1014
DynamicBehavioralModelingof3GPowerAmplifiersUsingReal-ValuedTime-DelayNeuralNetworks.... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... .. T.Liu,S.Boumaiza,andF.M.Ghannouchi 1025
NarrowBandpassFiltersUsingDual-BehaviorResonatorsBasedonStepped-ImpedanceStubsandDifferent-LengthStubs... ....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... ..... ... C.Quendo,E.Rius,andC.Person 1034
DesignofNarrow-BandDBRPlanarFiltersinSi–BCBTechnologyforMillimeter-WaveApplications ...... ...... ..... ....
...... ..... ...... ...... ...... .....G.Prigent,E.Rius,F.LePennec,S.LeMaguer,C.Quendo,G.Six,andH.Happy 1045
StudyontheStabilityandNumericalDispersionoftheFDTDTechniqueIncludingLumpedInductors ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...... ...... ...... ..... .. J.A.Pereda,Á.Vegas,andA.Prieto 1052
AnalysisofCoupledPhase-LockedLoopsWithIndependentOscillatorsforBeamControlActivePhasedArrays ........ H.-C.Chang 1059
AGeneralizedLocalTime-StepSchemeforEfficientFVTDSimulationsinStronglyInhomogeneousMeshes . ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...... ...C.Fumeaux,D.Baumann,P.Leuchtmann,andR.Vahldieck 1067
60%Efficient10-GHzPowerAmplifierWithDynamicDrainBiasControl .. ...... ..... ...... ...... ...... ..... ....
...... ..... ...... ...... ...... ..... ...... ...N.Wang,V.Yousefzadeh,D.Maksimovic´,S.Pajic´,andZ.B.Popovic´ 1077
ParallelCoupledMicrostripFiltersWithGround-PlaneApertureforSpuriousBandSuppressionandEnhancedCoupling..... ....
...... ..... ...... ...... ...... ..... ...... ...... ..M.delCastilloVelázquez-Ahumada,J.Martel,andF.Medina 1082
InformationforAuthors.. ...... ...... ..... ...... ...... ....... ........ ..... ...... ...... ...... ..... .... 1087
CALLSFORPAPERS
16thAsiaPacificMicrowaveConference .. ..... ...... ...... ...... ....... ....... ...... ...... ...... ..... .... 1088
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IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES,VOL.52,NO.3,MARCH2004 741
Editorial
THIS TRANSACTIONS begins with a Mini-Special Issue
of papers from the 2003 IEEE Microwave Theory and
Techniques Society (IEEE MTT-S) International Microwave
Symposium (IMS). The reviews and revisions of these papers
were not completed in time for them to be included in this
TRANSACTIONS’ December 2003 issue, which was devoted to
the IEEE MTT-S IMS. Thirty-seven papers were published in
thisTRANSACTIONS’December2003issue,fourintheJanuary
2004issueand13inthisissueforatotalof54papersbasedon
workpresentedattheIEEEMTT-SIMS.
OneoftheprioritiesintheeditingofthisTRANSACTIONShas
beenreducingthetimefrominitialsubmissionofamanuscript
byanauthortothetimeitispublished.ThegoaloftheIEEEis
toachieveanine-monthturnaround,whichcorrespondstoap-
proximately39weeks.Wehavereducedthecycletimeofthis
TRANSACTIONS,seeFig.1,totheIEEEgoalandthisishowwe
Fig.1. Delayinweeksfromsubmissiontopublication.Theabscissaindicates
didit.Amanuscriptmustbesubmittedasapdffileofnomore themonthandyearofpublication.
than1MBinsizeemailedtotheeditor-in-chief(EIC)atTMT-
[email protected]. When a paper is received, the EIC reads it
andrequestsobviouschangesfromtheauthor.Thepaperisthen
senttooneofthisTRANSACTIONS’AssociateEditorstohandle
the editingprocess orthe EIC handles it himself. Manuscripts
are then sent to five reviewers, some of which, unfortunately
never respond. All this interaction is done via email using pdf
files rather than relying on a centralized manuscript-handling
system.Itisapersonalizedprocessandrelationshipsareestab-
lishedbetweentheeditors,authors,andreviewers.Mostreviews
arereceivedbackinfourweeks,althoughwithinvolvedpapers,
itcantakeuptotwomonthsormoretoreceiveadequatereviews.
Mostpapersmustberevised,thus,finaldispositionstakefrom
three to six months, which includes the time for the author to
revisethemanuscript.Itthentakesfromonetofourweeksfor
Fig.2. Distribution of paperspublished in 2003 by country of origin. The
anauthortosendthefinalversionofthemanuscripttotheEIC.
numberinparenthesisistheIEEERegion,therearesixregionsintheUSA.
Onceamonth,anissueisassembledbytheEICandsenttothe
IEEEwhereitistypesetandotherwisemadereadyforprinting.
Generally,anissueissenttotheprinteronetotwoweeksbefore
themonthofpublicationandmailedpriortothemonthofpub-
lication. The exceptions to this are the December and January
issues.TheDecemberissueisdelayed,initiallybecauseitisthe
largest issue of the year, as it is devoted to papers originating
fromtheIEEEMTT-SIMS,andsecond,becauseindexing(pub-
lished annually at the end of this TRANSACTIONS’ December
issue) must be done after the issue is complete. Overall, the
best that can be achieved is to process a manuscript from ini-
tialsubmissiontoprintinsixmonths.Specialissuesgenerally
takelonger,astheymustwaituntilallofthepaperssubmitted Fig.3. Distributionofpaperspublishedin2003bysource.
to the special issue are considered. Thus, we expect that the
nine-monthcycletimemaybeimprovedbyamonthorso,but devotedtoconferenceswillbehandledthroughthenormaledi-
notbymuchmore.Oneoftheconsequencesofthefasterturn- torialprocess.Thiswillenableustomaintainarapidpublication
aroundthatweareachievingisthattheeditingofspecialissues schedule.
Figs. 2–4summarize the distributionof paperspublished in
thisTRANSACTIONSin2003.VeryfewpapersoriginatedinCen-
DigitalObjectIdentifier10.1109/TMTT.2004.823530 tralandSouthAmericaandAfrica.Giventhis, Fig.2 indicates
0018-9480/04$20.00©2004IEEE
742 IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES,VOL.52,NO.3,MARCH2004
letters to the editor reporting corrections or commenting on
paperspreviouslypublishedinthisTRANSACTIONS.
ThisTRANSACTIONSmaintainsawebsiteathttp://www.mtt.
org/publications/Transactions/transactions.htmwhereCallsfor
Papers for special issues and links to author tools are main-
tained.CurrentCallsforPapersareasfollows:
1) SpecialIssueoftheTransactionsontheIEEEMTT-SIn-
ternationalMicrowaveSymposium.Deadlineforsubmis-
sionofmanuscripts:21April2004;scheduledpublication
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2) SpecialIssueoftheTransactionsonMultifunctionalRF
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TABLE I
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IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES,VOL.52,NO.3,MARCH2004 743
60-GHz-Band Coplanar MMIC Active Filters
MasaharuIto,Member,IEEE,KenichiMaruhashi,Member,IEEE,ShuyaKishimoto,andKeiichiOhata,Member,IEEE
Abstract—Thispaper presentsthedesignand performanceof
60-GHz-band coplanar monolithic microwave integrated circuit
(MMIC) active filters. To compensate for the loss of the passive
filter, a resonator composed of a quarter-wavelength line is
terminatedbyacircuitwithaconstantnegativeresistanceovera
wide frequency band. Cross-coupling is introduced to make the
attenuationpolesonbothsidesofthepassband.Wedeveloptwo
types of two-stage filter: one with medium bandwidth and the
otherwithnarrowbandwidth.Theformershowsaninsertionloss
of 3.0 dB with a 3-dB bandwidth of 2.6 GHz and a rejection of
Fig.1. Quarter-wavelengthresonatorterminatedbynegativeresistance.
largerthan20dBata3-GHzseparationfromacenterfrequency
of 65.0 GHz. This filter also shows a noise figure of 10.5 dB.
The latter filter shows an insertion loss of 2.8 dB with a 10-dB [10], [11]. We devised a negative-resistance circuit configura-
bandwidthof2.1GHzatacenterfrequencyof65.0GHz.Italso tiontoobtainaconstantvalueoverawidefrequencybandfor
showsanoutputpowerof5.0dBmata1-dBcompressionpoint. stable operation. We confirmed loss compensation without in-
The loss variation due to temperature variation is successfully
stabilityandoscillationduetothenegativeresistanceofthefab-
compensated using a gate bias control circuit. The size of the
ricatedfilters.Wealsoattainedremarkablesizereduction,com-
MMICfiltersis2.5mm 1.1mm.
pared with the passive filter with planar dielectric resonators
Index Terms—Active filters, bandpass filters, coplanar wave-
[12]usedinourtransceivermodule.Tothebestofourknowl-
guides,negative-resistancecircuits.
edge,thesearethehighestfrequencyactivefiltersyetreported.
I. INTRODUCTION II. ACTIVEFILTERDESIGN
THE increasing demand for high-speed multimedia links, Manyresearchershavereportedactivefiltersbasedonvarious
such as wireless local area networks [1] and wireless approaches,suchasatransversalandrecursivefilterapproach
home networks [2], has stimulated the development of mil- [3], [4], an approach of cascade connections of passive filters
limeter-wave transceivers. For these systems, filters are key withamplifiers[5],anegative-resistanceapproach[6]–[8],and
componentsthatcansufficientlysuppressspurioussignalsout an active matching approach [9]. We adopt the negative-resis-
of the communication band. Essentially, filters need to have tance approach among them, which is simplest and most suit-
low insertion loss and high selectivity and, conventionally, ableforthemillimeter-waveband.
waveguidefiltersarewidelyusedtosatisfytheserequirements.
However, their bulky structure makes integration with mono- A. LossCompensation
lithicmicrowaveintegratedcircuits(MMICs)inthetransceiver
Fig. 1 shows a schematic that explains the principle of loss
module difficult and hinders the reduction of the module
compensationduetonegativeresistanceforaresonator.Theres-
size. On the contrary, planar filters are small, but have a loss
onatorconsistsofaquarter-wavelength line.Eachportof
issue, especially for narrow bandwidths. Active filters with a
theresonatorterminatesineitheranopenorshortcircuit.The
planar configuration are good candidates though because the
-factoroftheresonatorisdegradedbyohmic,dielectric,and
loss issue can be resolved. Filters are widely implemented by
radiation losses. The short-circuited terminal is replaced by a
an active filter approach at a microwave band [3]–[8]. At a
negative resistance to compensate for this loss. When the
millimeter-waveband,ontheotherhand,onlyoneactivefilter
linehasacharacteristicimpedance andanattenuationcon-
operatingat32GHzhasbeenreported[9].Thisisbecauseitis
stant ,theloss duetotheroundpathoftheresonatorisex-
difficulttoachievestableoperationoverwidefrequencies,i.e.,
pressedas(1).Thegain producedbythenegativeresistance
in-andout-of-bands.
isexpressedas(2).When issatisfied,resonatorloss
In this paper, we present two types of 60-GHz-band active
iscompletelycompensated andthe -factor isinfinite.Inthis
filterwithtworesonatorsterminatedbynegativeresistances.We
case,the negativeresistanceshouldsatisfy(3).Whenthe neg-
adoptedacoplanar-waveguideconfigurationbecauseitnotonly
ative resistance is larger than that given as follows by (3), the
eliminatesthebacksideprocess,unlikeamicrostrip-lineconfig-
resonatorhasaloop-gainandoscillationoccurs:
uration, butalsobecauseitis suitableforflip-chip technology
(1)
ManuscriptreceivedApril1,2003;revisedSeptember22,2003. (2)
TheauthorsarewiththePhotonicandWirelessDevicesResearchLabora-
tories,NECCorporation,Otsu,Shiga520-0833,Japan(e-mail:[email protected].
nec.com).
(3)
DigitalObjectIdentifier10.1109/TMTT.2004.823531
0018-9480/04$20.00©2004IEEE
744 IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES,VOL.52,NO.3,MARCH2004
theasymmetrictype,ontheotherhand,issmallerthanthatfor
the symmetric type. This is caused by the shunt capacitance
duetotheshortbarsonbothsidesoftheshuntstub.
The attenuation constant of the coplanar line with the
ground-to-grounddistanceof70 mwasestimatedbytheEM
simulatortobe0.039mm .Therequiredvalueofanegative
resistance is derived to be approximately 1 from
(3).However,theactuallyrequiredvalueshouldbelargerthan
1 in a negative direction considering the additional losses
attheI/Oandinter-stageconnections.
Fig.4showsthecalculatedimpedanceofthenegative-resis-
Fig.2. Schematicofnegative-resistancecircuit. tance circuit after lengths and were optimized.
Theresistancepart hasaconstantvalueofapproximately
2 at a of 0.3 V from 55 to 70 GHz. This maximum
B. Negative-ResistanceCircuit
negativevalueisdeterminedbytheshuntstublength atthein-
Negative resistance should not only satisfy (3), but should
ductivecoupling.Thisfigureshowsthatitsvaluecanbetuned
also be constant over a wide frequency range in order to
by the gate voltage with a constant value over this frequency
compensate for the resonator loss without causing instability
range.Onthecontrary,thevalueofthereactancepart isun-
andoscillation.Fig.2showstheschematicofanegative-resis-
changedbythegatevoltage.Thismeansthatwecanattaincom-
tance circuit using a field-effect transistor (FET) as an active
pletelosscompensationwhilemaintainingthecenterfrequency
device.Negativeresistanceisusuallyobtainedbyconnectinga
of the filter. The reactance part has a nonzero value. How-
capacitivelinetothesourceterminalathigherfrequenciesthan
ever,thesmall reactance canbe compensated bychangingthe
10 GHz. The capacitive line consists of a short-circuited line
length of the resonator with , where is derived
withlength , whichis longerthan a quarter-wavelength.To
from(4)usingthephaseconstant ofthecoplanarwaveguide
achieve a constant negative resistance over a wide frequency
asfollows:
band,weconnectedanothershort-circuitedlinewithlength
in parallel, which is shorter than the first capacitive line. The
(4)
upperfrequencylimitoftheband,wheretheimpedanceatthe
source terminal is capacitive,is unchanged because the length
InFig.4(b),thelength ata of 0.3Visalsoshown.
is shorter than the length . The frequency response in
The length is not constant over the entire frequency
thebandistuned,changingthelength .Asaresult,wecan
band, but increases in a negative direction with an increase
obtain a constant negative resistance over a wide frequency
in frequency. As a result, the compensation using a specific
band. In our configuration, we placed the output terminal on
value (e.g., 55 m at 60 GHz) decreases the bandwidth
the gate terminal side because here it can eliminate a large
of the filter, compared to that for the length , which is
drainbiasnetwork.Agatevoltage isappliedviaaresistance
constant over the frequency band. This helps in the design
with a large value of 3 K . The negative resistance is
of a narrow-bandwidth filter. The optimized parameters were
inductivelycoupledtoanoutsideresonator.
m, m, m, m,
In Fig. 3, two types of inductive coupling structure are
and m.
shown.Weusedacoplanarwaveguidewithaground-to-ground
distance of 70 m for the line. The first is a symmetric type
C. ActiveFilterCircuitDiagram
and is constructed by connecting the signal line and the two
ground planes of the coplanar line with shunt stubs, as shown Fig.5showsacircuitdiagramofatwo-stageactivefilter.Ca-
in Fig. 3(a). The second is an asymmetric type and the signal pacitivecouplingswereusedfortheI/Oandinter-stageconnec-
line is connected to only one ground plane with a shunt stub, tions.Weintroducedcross-couplingtoimprovethe skirtchar-
as shown in Fig. 3(b). For the asymmetric type, short bars acteristicofthefilter.Forthispurpose,inductivecouplingwas
connecting both ground planes are needed on both sides of incorporatedbetweentheI/Oportstomakeattenuationpoleson
the shunt stub to suppress excitation of a slot-line mode. bothsidesofthepassband.
We calculated these two types of coupling structure using a In this study, we developed two types of filter for different
three-dimensionalelectromagnetic(EM)simulatorandderived purposes in the transceiver. The first (type 1) was a medium-
theequivalentcircuitshowninFig.3(c).Fig.3(d)and(e)shows bandwidthfilterusedforthereceivermoduleanditsuppresses
theextractedshuntinductance andtheseriesinductance theleakagesignalfromthetransmittermoduleoperatingatdif-
oftheequivalentcircuit,respectively.Theshuntinductance , ferentfrequencies.Thesecond(type2)wasanarrow-bandwidth
whichmainlycausesthecoupling,isproportionaltotheshunt filterusedforthetransmittermoduleanditlimitsthebandwidth
stublength .Itsvaluefortheasymmetrictypeisapproximately ofthetransmittedsignal.Wedesignedfilterswiththespecifica-
fourtimeslargerthanthatforthesymmetrictypewiththesame tions summarized in Table I. We calculated the -parameters
length . This indicates that the asymmetric type enables the ofthepassivecomponents,suchasI/Oandinter-stageconnec-
coupling structure to be shrunk. The series inductance for tions,andaT-junctionbytheEMsimulator.
ITOetal.:60-GHz-BANDCOPLANARMMICACTIVEFILTERS 745
Fig. 3. Inductive coupling.(a) Symmetric structure. (b) Asymmetric structure. (c) Equivalentcircuit. (d) Shunt inductance of equivalentcircuit. (e) Series
inductanceofequivalentcircuit.
Fig. 6 shows a chip photograph of a fabricated MMIC ac- of70 mforthecoplanarresonatorsthan52 mfortheother
tive filter. The chip size is 2.5 mm 1.1 mm 0.15 mm. The linestoincreasethe factoroftheresonators.Furthermore,re-
volumeisapproximately1/7ofourplanardielectric-resonator gardingtheinductivecouplingbetweenthenegativeresistance
filter with a size of 3.4 mm 3.5 mm 0.25 mm [12]. The andresonator,oneoftwoshortbarsonbothsidesoftheshunt
activedevice is an AlGaAs/InGaAs heterojunctionfield-effect stubwaseliminated.Thisisbecausetherewasashortbaratthe
transistor(HJFET)withagatelengthof0.15 mandagatewidth T-shaped I/O coupling. This resulted in a further reduction in
of 50 m 2. We adopted a wider ground-to-ground distance resonatorloss.
746 IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES,VOL.52,NO.3,MARCH2004
III. EXPERIMENTALRESULTS
A. Small-SignalCharacteristics
Figs.7and8showthemeasuredsmall-signalcharacteristics
oftheactivefiltersfortypes1and2,respectively.Thegatebi-
asesweredeterminedtosatisfytheconditionthattheinsertion
loss was smallest with a factor of larger than one. Atten-
uation poles, due to cross-coupling, were clearly observed on
bothsidesofthepassbandandimprovedtheskirtcharacteristics
nearthepassband.Fortype1,thecharacteristicsforanunbiased
state(offstate)arealsoplottedinFig.7.Themeasuredinsertion
losswas3.0dBatacenterfrequencyof65.0GHzwitha3-dB
bandwidthof2.6GHzinabiasedstate(onstate).Therejection
oflargerthan20dBwasobtainedata3-GHzseparationfrom
thecenterfrequency.Consideringthefeederloss,whichcorre-
spondstothereturnlossinthestopband,theintrinsicinsertion
loss of the filter was estimated to be better than 1.5 dB. The
obtained on/off ratio, which is the ratio of the on to off state,
was better than 15 dB in the passband. For type 2, we fabri-
catedapassivefilterforcomparison,whichhasthesamestruc-
ture,exceptthenegative-resistancecircuitwasreplacedwitha
shortterminal.Fig.8alsoshowstheperformanceofthepassive
filter.Itwasfoundthatthelosswassuccessfullycompensated
bythenegative-resistancecircuit.Themeasuredon-stateinser-
tionlosswas2.8dBatacenterfrequencyof65.0GHzwitha
3-dBbandwidthof1.3GHzanda10-dBbandwidthof2.1GHz.
The off-state insertion and return losses were 23 and 3 dB at
thecenterfrequency,respectively.Theseobtainedresultsforthe
type-1andtype-2filtersmeetthedesignspecifications.During
themeasurements,weconfirmedthatinstabilityandoscillation
didnotoccur.Itwasinferredthatthenegative-resistancecircuit
hadastableconstantvalueoverthisfrequencyband.
Fig. 4. Calculated impedance of negative-resistance circuit. (a) Resistance
part.(b)Reactancepart.
B. NoisePerformance
Noise performance is important when considering the filter
forthereceivermodule.Fig.9showsthemeasurednoisefigure
for the type-1 filter. The noise figure of 10.5 dB was obtained
atthecenterfrequencyof65.0GHz.Thisrelativelyhighnoise
figure was caused due to the low factor of the passive res-
onator,anditcanbeimprovedbyenhancingthe factor[13].
Instead, when a low-noise amplifier is connected to the filter
input,thefilteriseasilyapplicableforthereceivermodule.For
instance,ifanamplifierwithagainof20dBandanoisefigure
of4dB[14]isconnected,theoverallnoisefigurewillbe4.2dB
andthenoisefigureofthefilterwillbenegligible.
C. Large-SignalCharacteristics
The type-2 filter for the transmitter module should have a
high tolerance for high input power. Fig. 10 shows the mea-
Fig.5. Schematicoftwo-stageactivefilterwithcross-coupling. sured large-signal characteristics. The output power at a 1-dB
compressionpoint was5.0dBmforaninputpower
of 8.8 dBm at the center frequency of 65.0 GHz. The filter is
TABLE I expectedtobeusedforourtransmittermodule,wheretheinput
DESIGNFILTERSPECIFICATIONS power is 5 dBm. Further improvement of power-handling ca-
pability, if necessary, is possible by using FETs with longer
gatewidths. The frequency response of the filter is shown at a
of9.7dBminFig.10(b).Thesmall-signalcharacteristics
arealsoshown.Thepassbandcharacteristicwasdegradedatthe